LMH6738
LMH6738 Very Wideband, Low Distortion Triple Op Amp
Literature Number: SNOSAC1D
LMH6738
Very Wideband, Low Distortion Triple Op Amp
General Description
The LMH6738 is a very wideband, DC coupled monolithic
operational amplifier designed specifically for ultra high reso-
lution video systems as well as wide dynamic range systems
requiring exceptional signal fidelity. Benefiting from Nation-
al’s current feedback architecture, the LMH6738 offers a
gain range of ±1to±10 while providing stable, operation
without external compensation, even at unity gain. At a gain
of +2 the LMH6738 supports ultra high resolution video
systems with a 400 MHz 2 V
PP
–3 dB Bandwidth. With 12-bit
distortion levels through 30 MHz (R
L
= 100Ω), 2.3 nV/
Hz input referred noise, the LMH6738 is the ideal driver or
buffer for high speed flash A/D and D/A converters. Wide
dynamic range systems such as radar and communication
receivers requiring a wideband amplifier offering exceptional
signal purity will find the LMH6738’s low input referred noise
and low harmonic distortion make it an attractive solution.
Features
n750 MHz −3 dB small signal bandwidth (A
V
= +1)
n−85 dBc 3rd harmonic distortion (20 MHz)
n2.3 nV/ Hz input noise voltage
n3300 V/µs slew rate
n33 mA supply current (11.3 mA per op amp)
n90 mA linear output current
n0.02/0.01 Diff. Gain / Diff. Phase (R
L
= 150Ω)
Applications
nRGB video driver
nHigh resolution projectors
nFlash A/D driver
nD/A transimpedance buffer
nWide dynamic range IF amp
nRadar/communication receivers
nDDS post-amps
nWideband inverting summer
nLine driver
Connection Diagram
16-Pin SSOP
20097510
Top View
VIP10™is a trademark of National Semiconductor Corporation.
April 2006
LMH6738 Very Wideband, Low Distortion Triple Op Amp
© 2006 National Semiconductor Corporation DS200975 www.national.com
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Supply Voltage (V
+
-V
–
) 13.2V
I
OUT
(Note 3)
Common Mode Input Voltage ±V
CC
Maximum Junction Temperature +150˚C
Storage Temperature Range −65˚C to +150˚C
Soldering Information
Infrared or Convection (20 sec.) 235˚C
Wave Soldering (10 sec.) 260˚C
ESD Tolerance (Note 4)
Human Body Model 2000V
Machine Model 200V
Storage Temperature Range −65˚C to +150˚C
Operating Ratings (Note 1)
Thermal Resistance
Package (θ
JC
)(θ
JA
)
16-Pin SSOP 36˚C/W 120˚C/W
Operating Temperature Range −40˚C +85˚C
Supply Voltage (V
+
-V
–
) 8V to 12V
Electrical Characteristics (Note 2)
A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless otherwise specified.
Symbol Parameter Conditions Min Typ Max Units
Frequency Domain Performance
UGBW -3 dB Bandwidth Unity Gain, V
OUT
= 200 mV
PP
750 MHz
SSBW -3 dB Bandwidth V
OUT
= 200 mV
PP
480 MHz
LSBW V
OUT
=2V
PP
400
0.1 dB Bandwidth V
OUT
=2V
PP
150 MHz
GFPL Peaking DC to 75 MHz 0 dB
GFR1 Rolloff DC to 150 MHz, V
OUT
=2V
PP
0.1 dB
GFR2 Rolloff @300 MHz, V
OUT
=2V
PP
1.0 dB
Time Domain Response
TRS Rise and Fall Time
(10% to 90%)
2V Step 0.9 ns
TRL 5V Step 1.7
SR Slew Rate 5V Step 3300 V/µs
t
s
Settling Time to 0.1% 2V Step 10 ns
t
e
Enable Time From Disable = rising edge. 7.3 ns
t
d
Disable Time From Disable = falling edge. 4.5 ns
Distortion
HD2L 2
nd
Harmonic Distortion 2 V
PP
, 5 MHz −80
dBcHD2 2 V
PP
, 20 MHz −71
HD2H 2 V
PP
, 50 MHz −55
HD3L 3
rd
Harmonic Distortion 2 V
PP
, 5 MHz −90
dBcHD3 2 V
PP
, 20 MHz −85
HD3H 2 V
PP
, 50 MHz −65
Equivalent Input Noise
V
N
Non-Inverting Voltage >1 MHz 2.3 nV/
I
CN
Inverting Current >1 MHz 12 pA/
N
CN
Non-Inverting Current >1 MHz 3 pA/
Video Performance
DG Differential Gain 4.43 MHz, R
L
= 150Ω.02 %
DP Differential Phase 4.43 MHz, R
L
= 150Ω.01 ˚
Static, DC Performance
VIO Input Offset Voltage (Note 6) 0.5 ±2.5
±4.5
mV
IBN Input Bias Current (Note 6) Non-Inverting −15
−20
−7 0
+5
µA
IBI Input Bias Current (Note 6) Inverting −2 ±25
±35
µA
LMH6738
www.national.com 2
Electrical Characteristics (Note 2) (Continued)
A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless otherwise specified.
Symbol Parameter Conditions Min Typ Max Units
PSRR Power Supply Rejection Ratio
(Note 6)
50
48.5
53 dB
CMRR Common Mode Rejection Ratio
(Note 6)
46
44
50 dB
XTLK Crosstalk Input Referred, f=10MHz, Drive
channels A,C measure channel
B
−80 dB
I
CC
Supply Current (Note 6) All three amps Enabled, No
Load
32 35
40
mA
Supply Current Disabled V
+
R
L
=∞1.9 2.2 mA
Supply Current Disabled V
−
R
L
=∞1.1 1.3 mA
Miscellaneous Performance
R
IN
+ Non-Inverting Input Resistance 1000 kΩ
C
IN
+ Non-Inverting Input Capacitance .8 pF
R
IN
− Inverting Input Impedance Output impedance of input
buffer.
30 Ω
R
O
Output Impedance DC 0.05 Ω
V
O
Output Voltage Range (Note 6) R
L
= 100Ω±3.25
±3.1
±3.5
V
R
L
=∞±3.65
±3.5
±3.8
CMIR Common Mode Input Range
(Note 6)
CMRR >40 dB ±1.9
±1.7
±2.0 V
I
O
Linear Output Current
(Notes 3, 6)
V
IN
= 0V, V
OUT
<±30 mV 80
60
90 mA
I
SC
Short Circuit Current (Note 5) V
IN
= 2V Output Shorted to
Ground
160 mA
I
IH
Disable Pin Bias Current High Disable Pin = V
+
10 µA
I
IL
Disable Pin Bias Current Low Disable Pin = 0V −350 µA
V
DMAX
Voltage for Disable Disable Pin ≤V
DMAX
0.8 V
V
DMIM
Voltage for Enable Disable Pin ≥V
DMIN
2.0 V
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables.
Note 2: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of
the device such that TJ=T
A. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self heating where TJ>TA.
See Applications Section for information on temperature de-rating of this device." Min/Max ratings are based on product characterization and simulation. Individual
parameters are tested as noted.
Note 3: The maximum output current (IOUT) is determined by device power dissipation limitations. See the Power Dissipation section of the Application Section for
more details.
Note 4: Human Body Model is 1.5 kΩin series with 100 pF. Machine Model is 0Ωin series with 200 pF.
Note 5: Short circuit current should be limited in duration to no more than 10 seconds. See the Power Dissipation section of the Application Section for more details.
Note 6: Parameter 100% production tested at 25˚ C.
Ordering Information
Package Part Number Package Marking Transport Media NSC Drawing
16-pin SSOP LMH6738MQ LH6738MQ 95 Units/Rail MQA16
LMH6738MQX 2.5k Units Tape and Reel
LMH6738
www.national.com3
Typical Performance Characteristics A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless other-
wise specified).
Large Signal Frequency Response Large Signal Frequency Response
20097520 20097528
Small Signal Frequency Response Frequency Response vs. V
OUT
20097513 20097501
Frequency Response vs. Supply Voltage Gain Flatness
20097516 20097530
LMH6738
www.national.com 4
Typical Performance Characteristics A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless otherwise
specified). (Continued)
Pulse Response Frequency Response vs. Capacitive Load
20097522 20097514
Series Output Resistance vs. Capacitive Load Open Loop Gain and Phase
20097519 20097526
Distortion vs. Frequency Distortion vs. Output Voltage
20097525
20097517
LMH6738
www.national.com5
Typical Performance Characteristics A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless otherwise
specified). (Continued)
Distortion vs. Supply Voltage CMRR vs. Frequency
20097518 20097511
PSRR vs. Frequency Crosstalk vs. Frequency
20097521 20097529
Closed Loop Output Impedance |Z| Disable Timing
20097504 20097524
LMH6738
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Typical Performance Characteristics A
V
= +2, V
CC
=±5V, R
L
= 100Ω,R
F
= 549Ω; unless otherwise
specified). (Continued)
DC Errors vs. Temperature Input Noise vs. Frequency
20097512 20097527
Disabled Channel Isolation vs. Frequency
20097531
LMH6738
www.national.com7
Application Section
GENERAL INFORMATION
The LMH6738 is a high speed current feedback amplifier,
optimized for very high speed and low distortion. The
LMH6738 has no internal ground reference so single or split
supply configurations are both equally useful.
EVALUATION BOARDS
National Semiconductor provides the following evaluation
boards as a guide for high frequency layout and as an aid in
device testing and characterization. Many of the datasheet
plots were measured with these boards.
Device Package Evaluation Board
Part Number
LMH6738MQA SSOP LMH730275
A bare evaluation board is shipped when a sample request is
placed with National Semiconductor.
FEEDBACK RESISTOR SELECTION
One of the key benefits of a current feedback operational
amplifier is the ability to maintain optimum frequency re-
sponse independent of gain by using appropriate values for
the feedback resistor (R
F
). The Electrical Characteristics and
Typical Performance plots specify an R
F
of 550Ω, a gain of
+2 V/V and ±5V power supplies (unless otherwise speci-
fied). Generally, lowering R
F
from it’s recommended value
will peak the frequency response and extend the bandwidth
while increasing the value of R
F
will cause the frequency
response to roll off faster. Reducing the value of R
F
too far
below it’s recommended value will cause overshoot, ringing
and, eventually, oscillation.
See Figure 3, Recommended R
F
. vs Gain for selecting a
feedback resistor value for gains of ±1to±10. Since each
application is slightly different it is worth some experimenta-
tion to find the optimal R
F
for a given circuit. In general a
value of R
F
that produces ~.1 dB of peaking is the best
compromise between stability and maximal bandwidth. Note
that it is not possible to use a current feedback amplifier with
the output shorted directly to the inverting input. The buffer
configuration of the LMH6738 requires a 750Ωfeedback
resistor for stable operation.
The LMH6738 was optimized for high speed operation. As
shown in Figure 3 the suggested value for R
F
decreases for
higher gains. Due to the impedance of the input buffer there
is a practical limit for how small R
F
can go, based on the
lowest practical value of R
G
. This limitation applies to both
inverting and non inverting configurations. For the LMH6738
the input resistance of the inverting input is approximately
30Ωand 20Ωis a practical (but not hard and fast) lower limit
for R
G
. The LMH6738 begins to operate in a gain bandwidth
limited fashion in the region where R
G
is nearly equal to the
input buffer impedance. Note that the amplifier will operate
with R
G
values well below 20Ω, however results may be
substantially different than predicted from ideal models. In
particular the voltage potential between the Inverting and
Non Inverting inputs cannot be expected to remain small.
Inverting gain applications that require impedance matched
inputs may limit gain flexibility somewhat (especially if maxi-
mum bandwidth is required). The impedance seen by the
source is R
G
|| R
T
(R
T
is optional). The value of R
G
is R
F
20097505
FIGURE 1. Recommended Non-Inverting Gain Circuit
20097506
FIGURE 2. Recommended Inverting Gain Circuit
20097503
FIGURE 3. Recommended R
F
vs. Gain
LMH6738
www.national.com 8
Application Section (Continued)
/Gain. Thus for an inverting gain of −7 V/V and an optimal
value for R
F
the input impedance is equal to 50Ω. Using a
termination resistor this can be brought down to match a
25Ωsource, however, a 150Ωsource cannot be matched. To
match a 150Ωsource would require using a 1050Ωfeedback
resistor and would result in reduced bandwidth.
For more information see Application Note OA-13 which
describes the relationship between R
F
and closed-loop fre-
quency response for current feedback operational amplifiers.
The value for the inverting input impedance for the LMH6738
is approximately 30Ω. The LMH6738 is designed for opti-
mum performance at gains of +1 to +10 V/V and −1 to −9
V/V. Higher gain configurations are still useful, however, the
bandwidth will fall as gain is increased, much like a typical
voltage feedback amplifier.
ACTIVE FILTER
When using any current feedback Operational Amplifier as
an active filter it is necessary to be careful using reactive
components in the feedback loop. Reducing the feedback
impedance, especially at higher frequencies, will almost cer-
tainly cause stability problems. Likewise capacitance on the
inverting input should be avoided. See Application Notes
OA-7 and OA-26 for more information on Active Filter appli-
cations for Current Feedback Op Amps.
When using the LMH6738 as a low pass filter the value of R
F
can be substantially reduced from the value recommended
in the R
F
vs. Gain charts. The benefit of reducing R
F
is
increased gain at higher frequencies, which improves at-
tenuation in the stop band. Stability problems are avoided
because in the stop band additional device bandwidth is
used to cancel the input signal rather than amplify it. The
benefit of this change depends on the particulars of the
circuit design. With a high pass filter configuration reducing
R
F
will likely result in device instability and is not recom-
mended.
DRIVING CAPACITIVE LOADS
Capacitive output loading applications will benefit from the
use of a series output resistor R
OUT
.Figure 5 shows the use
of a series output resistor, R
OUT
, to stabilize the amplifier
output under capacitive loading. Capacitive loads of 5 to 120
pF are the most critical, causing ringing, frequency response
peaking and possible oscillation. The charts “Suggested
R
OUT
vs. Cap Load” give a recommended value for selecting
a series output resistor for mitigating capacitive loads. The
values suggested in the charts are selected for .5 dB or less
of peaking in the frequency response. This gives a good
compromise between settling time and bandwidth. For appli-
cations where maximum frequency response is needed and
some peaking is tolerable, the value of R
OUT
can be reduced
slightly from the recommended values.
An alternative approach is to place Rout inside the feedback
loop as shown in Figure 6. This will preserve gain accuracy,
but will still limit maximum output voltage swing.
INVERTING INPUT PARASITIC CAPACITANCE
Parasitic capacitance is any capacitance in a circuit that was
not intentionally added. It comes about from electrical inter-
action between conductors. Parasitic capacitance can be
reduced but never entirely eliminated. Most parasitic capaci-
tances that cause problems are related to board layout or
lack of termination on transmission lines. Please see the
section on Layout Considerations for hints on reducing prob-
lems due to parasitic capacitances on board traces. Trans-
mission lines should be terminated in their characteristic
impedance at both ends.
High speed amplifiers are sensitive to capacitance between
the inverting input and ground or power supplies. This shows
up as gain peaking at high frequency. The capacitor raises
device gain at high frequencies by making R
G
appear
smaller. Capacitive output loading will exaggerate this effect.
In general, avoid introducing unnecessary parasitic capaci-
tance at both the inverting input and the output.
20097507
FIGURE 4. Typical Video Application
20097508
FIGURE 5. Decoupling Capacitive Loads
20097509
FIGURE 6. Series Output Resistor Inside
Feedback Loop
LMH6738
www.national.com9
Application Section (Continued)
One possible remedy for this effect is to slightly increase the
value of the feedback (and gain set) resistor. This will tend to
offset the high frequency gain peaking while leaving other
parameters relatively unchanged. If the device has a capaci-
tive load as well as inverting input capacitance using a series
output resistor as described in the section on “Driving Ca-
pacitive Loads” will help.
LAYOUT CONSIDERATIONS
Whenever questions about layout arise, use the evaluation
board as a guide. The LMH730275 is the evaluation board
supplied with samples of the LMH6738.
To reduce parasitic capacitances ground and power planes
should be removed near the input and output pins. Compo-
nents in the feedback loop should be placed as close to the
device as possible. For long signal paths controlled imped-
ance lines should be used, along with impedance matching
elements at both ends.
Bypass capacitors should be placed as close to the device
as possible. Bypass capacitors from each rail to ground are
applied in pairs. The larger electrolytic bypass capacitors
can be located farther from the device, the smaller ceramic
capacitors should be placed as close to the device as pos-
sible. The LMH6738 has multiple power and ground pins for
enhanced supply bypassing. Every pin should ideally have a
separate bypass capacitor. Sharing bypass capacitors may
slightly degrade second order harmonic performance, espe-
cially if the supply traces are thin and /or long. In Figure 1
and Figure 2 C
SS
is optional, but is recommended for best
second harmonic distortion. Another option to using C
SS
is to
use pairs of .01 µF and .1 µF ceramic capacitors for each
supply bypass.
VIDEO PERFORMANCE
The LMH6738 has been designed to provide excellent per-
formance with production quality video signals in a wide
variety of formats such as HDTV and High Resolution VGA.
NTSC and PAL performance is nearly flawless. Best perfor-
mance will be obtained with back terminated loads. The back
termination reduces reflections from the transmission line
and effectively masks transmission line and other parasitic
capacitances from the amplifier output stage. Figure 4
shows a typical configuration for driving a 75ΩCable. The
amplifier is configured for a gain of two to make up for the 6
dB of loss in R
OUT
.
POWER DISSIPATION
The LMH6738 is optimized for maximum speed and perfor-
mance in the small form factor of the standard SSOP-16
package. To achieve its high level of performance, the
LMH6738 consumes an appreciable amount of quiescent
current which cannot be neglected when considering the
total package power dissipation limit. The quiescent current
contributes to about 40˚ C rise in junction temperature when
no additional heat sink is used (V
S
=±5V, all 3 channels on).
Therefore, it is easy to see the need for proper precautions
to be taken in order to make sure the junction temperature’s
absolute maximum rating of 150˚C is not violated.
To ensure maximum output drive and highest performance,
thermal shutdown is not provided. Therefore, it is of utmost
importance to make sure that the T
JMAX
is never exceeded
due to the overall power dissipation (all 3 channels).
With the LMH6738 used in a back-terminated 75ΩRGB
analog video system (with 2 V
PP
output voltage), the total
power dissipation is around 435 mW of which 340 mW is due
to the quiescent device dissipation (output black level at 0V).
With no additional heat sink used, that puts the junction
temperature to about 140˚ C when operated at 85˚C ambi-
ent.
To reduce the junction temperature many options are avail-
able. Forced air cooling is the easiest option. An external
add-on heat-sink can be added to the SSOP-16 package, or
alternatively, additional board metal (copper) area can be
utilized as heat-sink.
An effective way to reduce the junction temperature for the
SSOP-16 package (and other plastic packages) is to use the
copper board area to conduct heat. With no enhancement
the major heat flow path in this package is from the die
through the metal lead frame (inside the package) and onto
the surrounding copper through the interconnecting leads.
Since high frequency performance requires limited metal
near the device pins the best way to use board copper to
remove heat is through the bottom of the package. A gap
filler with high thermal conductivity can be used to conduct
heat from the bottom of the package to copper on the circuit
board. Vias to a ground or power plane on the back side of
the circuit board will provide additional heat dissipation. A
combination of front side copper and vias to the back side
can be combined as well.
Follow these steps to determine the Maximum power dissi-
pation for the LMH6738:
1. Calculate the quiescent (no-load) power: P
AMP
=I
CC
*
(V
S
)V
S
=V
+
-V
−
2. Calculate the RMS power dissipated in the output stage:
P
D
(rms) = rms ((V
S
-V
OUT
)*I
OUT
) where V
OUT
and I
OUT
are the voltage and current across the external load and
V
S
is the total supply current
3. Calculate the total RMS power: P
T
=P
AMP
+P
D
The maximum power that the LMH6738, package can dissi-
pate at a given temperature can be derived with the following
equation (See Figure 7):
P
MAX
= (150o–T
AMB
)/ θ
JA
, where T
AMB
= Ambient tempera-
ture (˚C) and θ
JA
= Thermal resistance, from junction to
ambient, for a given package (˚C/W). For the SSOP package
θ
JA
is 120˚C/W.
20097502
FIGURE 7. Maximum Power Dissipation
LMH6738
www.national.com 10
Application Section (Continued)
ESD PROTECTION
The LMH6738 is protected against electrostatic discharge
(ESD) on all pins. The LMH6738 will survive 2000V Human
Body model and 200V Machine model events.
Under closed loop operation the ESD diodes have no effect
on circuit performance. There are occasions, however, when
the ESD diodes will be evident. If the LMH6738 is driven by
a large signal while the device is powered down the ESD
diodes will conduct.
The current that flows through the ESD diodes will either exit
the chip through the supply pins or will flow through the
device, hence it is possible to power up a chip with a large
signal applied to the input pins. Shorting the power pins to
each other will prevent the chip from being powered up
through the input.
LMH6738
www.national.com11
Physical Dimensions inches (millimeters)
unless otherwise noted
16-Pin SSOP
NS Package Number MQA16
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the right at any time without notice to change said circuitry and specifications.
For the most current product information visit us at www.national.com.
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LMH6738 Very Wideband, Low Distortion Triple Op Amp
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