CS5257A-1GDP5 - ON Semiconductor - Datasheet.Technology

September, 2006 − Rev. 10

1Publication Order Number:

CS5257A−1/D

CS5257A−1

7.0 A LDO 5−Pin Adjustable

Linear Regulator

This new very low dropout regulator is designed to power the next

generation of advanced microprocessors. To achieve very low

dropout, the internal pass transistor is powered separately from the

control circuitry. Furthermore, with the control and power inputs tied

together, this device can be used in single supply configuration and

still offer a better dropout voltage than conventional PNP−NPN based

LDO regulators. In this mode the dropout is determined by the

minimum control voltage.

It is supplied in five−terminal TO−220−5 and D2PAK−5 packages,

allowing for the implementation of a remote−sense pin permitting

very accurate regulation of output voltage directly at the load, where it

counts, rather than at the regulator. This remote sensing feature

virtually eliminates output voltage variations due to load changes and

resistive voltage drops. Typical load regulation measured at the sense

pin is 1.0 mV for an output voltage of 2.5 V with a load step of 10 mA

to 7.0 A.

The very fast transient loop response easily meets the needs of the

latest microprocessors. In addition, a small capacitor on the Adjust pin

will further improve the transient capabilities.

Internal protection circuitry provides for “bust−proof” operation,

similar to three−terminal regulators. This circuitry, which includes

overcurrent, short circuit, supply sequencing and overtemperature

protection will self protect the regulator under all fault conditions.

The CS5257A−1 is ideal for generating a secondary 2.0 V − 2.5 V

low voltage supply on a motherboard where both 5.0 V and 3.3 V are

already available.

Features

•1.25 V to 5.0 V VOUT at 7.0 A

•VPOWER Dropout < 0.35 V @ 7.0 A

•VCONTROL Dropout < 1.1 V @ 7.0 A

•1.5% Trimmed Reference

•Fast Transient Response

•Remote Voltage Sensing

•Thermal Shutdown

•Current Limit

•Short Circuit Protection

•Drop−In Replacement for LT1580

•Backwards Compatible with 3−Pin Regulators

MARKING DIAGRAMS

A = Assembly Location

WL, L = Wafer Lot

YY, Y = Year

WW, W = Work Week

TO−220−5

T SUFFIX

CASE 314D Tab = VOUT

Pin 1. VSENSE

2. Adjust

3. VOUT

4. VCONTR

5. VPOWER

CS5257A−1

AWLYWW

Device Package Shipping†

ORDERING INFORMATION

CS5257A−1GT5 TO−220−550 Units/Rail

D2PAK−5

DP SUFFIX

CASE 936AC

5257A−1

AWLYWW

D2PAK−5TO−220−5

CS5257A−1GDP5 D2PAK−5 50 Units/Rail

CS5257A−1GDPR5 D2PAK−5750 Tape & Reel

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†For information on tape and reel specifications,

including part orientation and tape sizes, please

refer to our Tape and Reel Packaging Specifications

Brochure, BRD8011/D.

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Figure 1. Application Diagram

CS5257A−1

10 mF

10 V

VCONTROL

VPOWER

VOUT

VSENSE

Adjust

100 mF

5.0 V

0.1 mF

5.0 V

3.3 V

124

1.0%

124

1.0%

Load

2.5 V @ 7.0 A

300 mF

5.0 V

MAXIMUM RATINGS*

Rating Value Unit

VPOWER Input Voltage 6.0 V

VCONTROL Input Voltage 13 V

Operating Junction Temperature Range, TJ0 to 150 °C

Storage Temperature Range −65 to +150 °C

ESD Damage Threshold 2.0 kV

Lead Temperature Soldering: Wave Solder (through hole styles only) Note 1

Reflow (SMD styles only) Note 2

260 peak

230 peak

°C

1. 10 second maximum.

2. 60 second maximum above 183°C.

*The maximum package power dissipation must be observed.

ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless

otherwise specified.)

Characteristic Test Conditions Min Typ Max Unit

CS5257A−1

Reference Voltage VCONTROL = 2.75 V to 12 V, VPOWER = 2.05 V to 5.5 V,

10 mA ≤ IOUT ≤ 7.0 A

1.234

(−1.5%)

1.253 1.272

(+1.5%)

Line Regulation VCONTROL = 2.5 V to 12 V, VPOWER = 1.75 V to 5.5 V,

IOUT = 10 mA

−0.02 0.2 %

Load Regulation (Note 3) VCONTROL = 2.75 V, VPOWER = 2.05 V,

IOUT = 10 mA to 7.0 A, with Remote Sense

−0.04 0.2 %

Minimum Load Current (Note 4) VCONTROL = 5.0 V, VPOWER = 3.3 V, DVOUT = +1.0% −5.0 10 mA

Control Pin Current (Note 5) VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 100 mA

VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 4.0 A

VCONTROL = 2.75 V, VPOWER = 1.75 V, IOUT = 4.0 A

VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 7.0 A

−

6.0

180

Adjust Pin Current VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 10 mA −60 120 mA

Current Limit VCONTROL = 2.75 V, VPOWER = 2.05 V, DVOUT = −1.5% 7.1 10 −A

3. This parameter is guaranteed by design and is not 100% production tested.

4. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set

the output voltage is selected to meet the minimum load current requirement.

5. The VCONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100

ratio. The minimum value is equal to the quiescent current of the device.

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ELECTRICAL CHARACTERISTICS (continued) (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless

otherwise specified.)

Characteristic UnitMaxTypMinTest Conditions

CS5257A−1

Short Circuit Current VCONTROL = 2.75 V, VPOWER = 2.05 V, VOUT = 0 V 5.0 9.0 −A

Ripple Rejection (Note 6) VCONTROL = VPOWER = 3.25 V

VRIPPLE = 1.0 VP−P @ 120 Hz, IOUT = 4.0 A,

CADJ = 0.1 mF

60 80 −dB

Thermal Regulation 30 ms Pulse, TA = 25°C−0.002 −%/W

VCONTROL Dropout Voltage

(Minimum VCONTROL − VOUT)

(Note 7)

VPOWER = 2.05 V, IOUT = 100 mA

VPOWER = 2.05 V, IOUT = 1.0 A

VPOWER = 2.05 V, IOUT = 2.75 A

VPOWER = 2.05 V, IOUT = 4.0 mA

VPOWER = 2.05 V, IOUT = 7.0 A

−

1.00

1.10

1.15

1.25

VPOWER Dropout Voltage

(Minimum VPOWER − VOUT)

(Note 7)

VCONTROL = 2.75 V, IOUT = 100 mA

VCONTROL = 2.75 V, IOUT = 1.0 A

VCONTROL = 2.75 V, IOUT = 2.75 A

VCONTROL = 2.75 V, IOUT = 4.0 mA

VCONTROL = 2.75 V, IOUT = 7.0 A

−

0.10

0.15

0.20

0.26

0.35

0.15

0.20

0.30

0.40

0.65

RMS Output Noise Freq = 10 Hz to 10 kHz, TA = 25°C−0.003 −%VOUT

Temperature Stability − − 0.5 −%

Thermal Shutdown (Note 8) −150 180 210 °C

Thermal Shutdown Hysteresis − − − 25 °C

VCONTROL Supply Only Output

Current

VCONTROL = 13 V, VPOWER Not Connected,

VADJ = VOUT = VSENSE = 0 V

− − 50 mA

VPOWER Supply Only Output

Current

VPOWER = 6.0 V, VCONTROL Not Connected,

VADJ = VOUT = VSENSE = 0 V

−0.1 1.0 mA

6. This parameter is guaranteed by design and is not 100% production tested.

7. Dropout is defined as either minimum control voltage (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential re-

quired to maintain 1.5% regulation at a particular load.

8. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test

is performed on each part.

PACKAGE PIN DESCRIPTION

PACKAGE PIN #

PIN SYMBOL FUNCTION

TO−220−5D

2PAK−5

1 1 VSENSE This Kelvin sense pin allows for remote sensing of the output voltage at the load for im-

proved regulation. It is internally connected to the positive input of the voltage sensing error

amplifier.

2 2 Adjust This pin is connected to the low side of the internally trimmed 1.5% bandgap reference volt-

age and carries a bias current of about 50 mA. A resistor divider from Adjust to VOUT and

from Adjust to ground sets the output voltage. Also, transient response can be improved by

adding a small bypass capacitor from this pin to ground.

3 3 VOUT This pin is connected to the emitter of the power pass transistor and provides a regulated

voltage capable of sourcing 7.0 A of current.

4 4 VCONTROL This is the supply voltage for the regulator control circuitry. For the device to regulate, this

voltage should be between 1.0 V and 1.25 V (depending on the output current) greater than

the output voltage. The control pin current will be about 1.0% of the power pin output current.

5 5 VPOWER This is the power input voltage. This pin is physically connected to the collector of the power

pass transistor. For the device to regulate, this voltage should be between 0.1 V and 0.65 V

greater than the output voltage depending on the output current. The output load current of

7.0 A is supplied through this pin.

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Figure 2. Block Diagram

−

BIAS

and

TSD

VREF

EA IA

VOUT

VSENSE

Adjust

VPOWER

VCONTROL

TYPICAL PERFORMANCE CHARACTERISTICS

Figure 3. Reference Voltage vs Temperature

TJ (°C)

10 30

Output Voltage Deviation (%)

−0.150

−0.050

0.100

−0.100

20 40 130

IO = 10 mA

VCONTROL = 2.75 V

VPOWER = 2.05 V

0.050

−0.075

0.075

−0.125

−0.025

0.025

50 7060 80 90 110100 120

Figure 4. Load Regulation vs Output Current

Figure 5. Transient Response Figure 6. Short Circuit Current vs VPOWER − VOUT

VPOWER − VOUT (V)

0 1.0

Output Current (A)

6.0

8.0

14.0

2.0

4.0

10.0

12.0

2.0 3.0 4.0 5.00.5 1.5 2.5 3.5 4.5 5.5

VCONTROL = 2.75 V

0 1.0 3.02.0 7.0

Output Current (A)

4.0 6.05.0

Output Voltage Deviation (%)

0.10

0.09

0.08

0.07

0.06

0.05

0.04

0.03

0.02

0.01

VPOWER = 2.05 V

VCONTROL = 2.75 V

Time (ms)

Output Voltage

Deviation (mV)

100

COUT = 330 mF

CPOWER = 110 mF

CCONTROL = 10 mF

CADJ = 0.1 mF

VCONTROL = 5.0 V

VPOWER = 3.3 V

VOUT = 2.5 V

01234

−50

−100

7.0

Current (A)

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Figure 7. Adjust Pin Current vs Temperature

Temperature (°C)

Adjust Pin Current (mA)

0 40 60 80 100

65 120 140 160

Figure 8. Minimum Load Current vs VCONTROL − VOUT

VCONTROL − VOUT (V)

1.0 3.0

Minimum Load Current (mA)

800

1000

1050

1200

900

950

1100

1150

5.0 7.0 9.02.0 4.0 6.0 8.0 10 11

VPOWER = 3.3 V

DVOUT = +1.0%

850

Figure 9. Adjust Pin Current vs VCONTROL − VOUT

VCONTROL − VOUT (V)

1.0 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 10 11

Adjust Pin Current (mA)

VPOWER = 2.05 V

IL = 10 mA

Figure 10. Ripple Rejection vs Frequency

VIN − VOUT = 2.0 V

IOUT = 4.0 A

VRIPPLE = 1.0 VP−P

COUT = 22 mF

CADJ = 0.1 mF

101

Frequency (Hz)

Ripple Rejection (dB)

102103104105106

VPOWER − VOUT (V)

0.5 1.5 2.5 3.5 4.5

Adjust Pin Current (mA)

VCONTROL = 2.75 V

IL = 10 mA

Figure 11. Adjust Pin Current vs VPOWER − VOUT Figure 12. VCONTROL Dropout Voltage vs IOUT

0 1.0 3.02.0 7.0

Output Current (A)

4.0 6.05.0

VCONTROL Dropout Voltage (V)

1.25

1.00

0.75

0.50

0.25

VPOWER = 2.05 V

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Figure 13. VPOWER Dropout Voltage vs IOUT

VPOWER − VOUT (V)

0.5 1.5 2.5 3.5 4.5

Minimum Load Current (mA)

915.4

916.0

916.1

916.2

916.3

916.4

915.5

915.6

915.7

915.8

915.9

VCONTROL = 5.0 V

DVOUT = +1.0%

Figure 14. Minimum Load Current vs VPOWER − VOUT

Figure 15. Adjust Pin Current vs Output Current

0 1.0 3.02.0 7.0

Output Current (A)

4.0 6.05.0

VPOWER Dropout Voltage (V)

1.0

0.9

0.8

0.7

0.6

0.5

0.4

0.3

0.2

0.1

VCONTROL = 2.75 V

Adjust Pin Current (mA)

72 0 1.0 3.02.0 8.0

Output Current (A)

4.0 6.05.0 7.0

VPOWER = 2.05 V

VCONTROL = 2.75 V

APPLICATIONS NOTES

THEORY OF OPERATION

The CS5257A−1 linear regulator provides adjustable

voltages from 1.25 V to 5.0 V at currents up to 7.0 A. The

regulator is protected against short circuits, and includes a

thermal shutdown circuit with hysteresis. The output, which

is current limited, consists of a PNP − NPN transistor pair

and requires an output capacitor for stability. A detailed

procedure for selecting this capacitor is included in the

Stability Considerations section.

VPOWER Function

The CS5257A−1 utilizes a two supply approach to

maximize efficiency. The collector of the power device is

brought out to the VPOWER pin to minimize internal power

dissipation under high current loads. VCONTROL provides

power for the control circuitry and the drive for the output

NPN transistor. VCONTROL should be at least 1.0 V greater

than the output voltage. Special care has been taken to ensure

that there are no supply sequencing problems. The output

voltage will not turn on until both supplies are operating. If

the control voltage comes up first, the output current will be

typically limited to about 3.0 mA until the power input

voltage comes up. If the power input voltage comes up first

the output will not turn on at all until the control voltage

comes up. The output can never come up unregulated.

The CS5257A−1 can also be used as a single supply

device with the control and power inputs tied together. In

this mode, the dropout will be determined by the minimum

control voltage.

Output Voltage Sensing

The CS5257A−1 five terminal linear regulator includes a

dedicated VSENSE function. This allows for true Kelvin

sensing of the output voltage. This feature can virtually

eliminate errors in the output voltage due to load regulation.

Regulation will be optimized at the point where the sense pin

is tied to the output.

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DESIGN GUIDELINES

Adjustable Operation

This LDO adjustable regulator has an output voltage

range of 1.25 V to 5.0 V. An external resistor divider sets the

output voltage as shown in Figure 16. The regulator’s

voltage sensing error amplifier maintains a fixed 1.253 V

reference between the output pin and the adjust pin.

Figure 16. An External Resistor Divider Sets the

Value of VOUT

. The 1.253 V Reference Voltage

Drops Across R1.

CS5257A−1

VCONTROL

VPOWER

VOUT

VSENSE

Adjust

A resistor divider network R1 and R2 causes a fixed

current to flow to ground. This current creates a voltage

across R2 that adds to the 1.253 V across R1 and sets the

overall output voltage. The adjust pin current (typically

50 mA) also flows through R2 and adds a small error that

should be taken into account if precise adjustment of VOUT

is necessary. The output voltage is set according to the

formula:

VOUT +1.253 V R1 )R2

R1 )R2 IADJ

The term IADJ × R2 represents the error added by the

adjust pin current. R1 is chosen so that the minimum load

current is a least 10 mA. R1 and R2 should be of the same

composition for best tracking over temperature. The divider

resistors should be placed physically as close to the load as

possible.

While not required, a bypass capacitor connected between

the adjust pin and ground will improve transient response

and ripple rejection. A 0.1 mF tantalum capacitor is

recommended for “first cut” design. Value and type may be

varied to optimize performance vs. price.

Other Adjustable Operation Considerations

The CS5257A−1 linear regulator has an absolute

maximum specification of 6.0 V for the voltage difference

between VIN and VOUT. However, the IC may be used to

regulate voltages in excess of 6.0 V. The two main

considerations in such a design are the sequencing of power

supplies and short circuit capability.

Power supply sequencing should be such that the

VCONTROL supply is brought up coincidentally with or

before the VPOWER supply. This allows the IC to begin

charging the output capacitor as soon as the VPOWER to

VOUT differential is large enough that the pass transistor

conducts. As VPOWER increases, the pass transistor will

remain in dropout, and current is passed to the load until

VOUT is in regulation. Further increase in the supply voltage

brings the pass transistor out of dropout. In this manner, any

output voltage less than 13 V may be regulated, provided the

VPOWER to VOUT differential is less than 6.0 V. In the case

where VCONTROL and VPOWER are shorted, there is no

theoretical limit to the regulated voltage as long as the

VPOWER to VOUT differential of 6.0 V is not exceeded.

There is a possibility of damaging the IC when VPOWER

− VIN is greater than 6.0 V if a short circuit occurs. Short

circuit conditions will result in the immediate operation of

the pass transistor outside of its safe operating area.

Overvoltage stresses will then cause destruction of the pass

transistor before overcurrent or thermal shutdown circuitry

can become active. Additional circuitry may be required to

clamp the VPOWER to VOUT differential to less than 6.0 V

if fail safe operation is required. One possible clamp circuit

is illustrated in Figure 17; however, the design of clamp

circuitry must be done on an application by application

basis. Care must be taken to ensure the clamp actually

protects the design. Components used in the clamp design

must be able to withstand the short circuit condition

indefinitely while protecting the IC.

Figure 17. Example Clamp Circuitry for

VPOWER − VOUT > 6.0 V

VCONTROL

VPOWER

VSENSE

VOUT

VADJ

External Supply

Stability Considerations

The output compensation capacitor helps determine three

main characteristics of a linear regulator: start−up delay,

load transient response, and loop stability.

The capacitor value and type is based on cost, availability,

size and temperature constraints. A tantalum or aluminum

electrolytic capacitor is best, since a film or ceramic

capacitor with almost zero ESR can cause instability. The

aluminum electrolytic capacitor is the least expensive

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solution. However, when the circuit operates at low

temperatures, both the value and ESR of the capacitor will

vary considerably. The capacitor manufacturer’s data sheet

provides this information.

A 300 mF tantalum capacitor will work for most

applications, but with high current regulators such as the

CS5257A−1 the transient response and stability improve

with higher values of capacitor. The majority of applications

for this regulator involve large changes in load current so the

output capacitor must supply the instantaneous load current.

The ESR of the output capacitor causes an immediate drop

in output voltage given by:

DV+DI ESR

For microprocessor applications it is customary to use an

output capacitor network consisting of several tantalum and

ceramic capacitors in parallel. This reduces the overall ESR

and reduces the instantaneous output voltage drop under

transient load conditions. The output capacitor network

should be as close to the load as possible for the best results.

Protection Diodes

When large external capacitors are used with a linear

regulator it is sometimes necessary to add protection diodes.

If the input voltage of the regulator gets shorted, the output

capacitor will discharge into the output of the regulator. The

discharge current depends on the value of the capacitor, the

output voltage, and the rate at which VCONTROL drops. In

the CS5257A−1 regulator, the discharge path is through a

large junction and protection diodes are not usually needed.

If the regulator is used with large values of output

capacitance and the input voltage is instantaneously shorted

to ground, damage can occur. In this case, a diode connected

as shown in Figure 18 is recommended.

Figure 18. Diode Protection Against VCONTROL

Short Circuit Conditions

CS5257A−1

VCONTROL

VPOWER

VOUT

VSENSE

Adjust

Use of the diode has the added benefit of bleeding VOUT

to ground if VCONTROL is shorted. This prevents an

unregulated output from causing system damage.

A rule of thumb useful in determining if a protection diode

is required is to solve for current

I+C V

where:

I is the current flow out of the load capacitance when

VCONTROL is shorted,

C is the value of load capacitance,

V is the output voltage, and

T is the time duration required for VCONTROL to transition

from high to being shorted.

If the calculated current is greater than or equal to the

typical short circuit current value provided in the

specifications, serious thought should be given to the use of

a protection diode.

Current Limit

The internal current limit circuit limits the output current

under excessive load conditions.

Short Circuit Protection

The device includes short circuit protection circuitry that

clamps the output current at approximately two amperes less

than its current limit value. This provides for a current

foldback function, which reduces power dissipation under a

direct shorted load.

Thermal Shutdown

The thermal shutdown circuitry is guaranteed by design to

activate above a die junction temperature of approximately

150°C and to shut down the regulator output. This circuitry

has 25°C of typical hysteresis, thereby allowing the

regulator to recover from a thermal fault automatically.

Calculating Power Dissipation and

Heat Sink Requirements

High power regulators such as the CS5257A−1 usually

operate at high junction temperatures. Therefore, it is

important to calculate the power dissipation and junction

temperatures accurately to ensure that an adequate heat sink

is used. Since the package tab is connected to VOUT on the

CS5257A−1, electrical isolation may be required for some

applications. Also, as with all high power packages, thermal

compound in necessary to ensure proper heat flow. For

added safety, this high current LDO includes an internal

thermal shutdown circuit.

The thermal characteristics of an IC depend on the

following four factors: junction temperature, ambient

temperature, die power dissipation, and the thermal

resistance from the die junction to ambient air. The

maximum junction temperature can be determined by:

TJ(max) +TA(max) )PD(max) RQJA

The maximum ambient temperature and the power

dissipation are determined by the design while the

maximum junction temperature and the thermal resistance

depend on the manufacturer and the package type. The

maximum power dissipation for a regulator is:

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PD(max) +(VIN(max) *VOUT(min))IOUT(max)

)VIN(max) IIN(max)

A heat sink effectively increases the surface area of the

package to improve the flow of heat away from the IC and

into the surrounding air. Each material in the heat flow path

between the IC and the outside environment has a thermal

resistance which is measured in degrees per watt. Like series

electrical resistances, these thermal resistances are summed

to determine the total thermal resistance between the die

junction and the surrounding air, RqJA. This total thermal

resistance is comprised of three components. These resistive

terms are measured from junction to case (RqJC), case to heat

sink (RqCS), and heat sink to ambient air (RqSA). The

equation is:

RQJA +RQJC )RQCS )RQSA

The value for RqJC is 1.4°C/watt for the CS5257A−1 in

both the TO−220−5 and D2PAK−5 packages. For a high

current regulator such as the CS5257A−1 the majority of

heat is generated in the power transistor section. The value

for RqSA depends on the heat sink type, while the RqCS

depends on factors such as package type, heat sink interface

(is an insulator and thermal grease used?), and the contact

area between the heat sink and the package. Once these

calculations are complete, the maximum permissible value

of RqJA can be calculated and the proper heat sink selected.

For further discussion on heat sink selection, see our

application note “Thermal Management,” document

number AND8036/D, available through the Literature

Distribution Center or via our website at

http://www.onsemi.com.

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PACKAGE DIMENSIONS

TO−220−5

T SUFFIX

CASE 314D−04

ISSUE E

−Q−

12345

5 PL

0.356 (0.014) T

SEATING

PLANE

−T−

DIM MIN MAX MIN MAX

MILLIMETERSINCHES

A0.572 0.613 14.529 15.570

B0.390 0.415 9.906 10.541

C0.170 0.180 4.318 4.572

D0.025 0.038 0.635 0.965

E0.048 0.055 1.219 1.397

G0.067 BSC 1.702 BSC

H0.087 0.112 2.210 2.845

J0.015 0.025 0.381 0.635

K0.990 1.045 25.146 26.543

L0.320 0.365 8.128 9.271

Q0.140 0.153 3.556 3.886

U0.105 0.117 2.667 2.972

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI

Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

3. DIMENSION D DOES NOT INCLUDE

INTERCONNECT BAR (DAMBAR) PROTRUSION.

DIMENSION D INCLUDING PROTRUSION SHALL

NOT EXCEED 10.92 (0.043) MAXIMUM.

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PACKAGE DIMENSIONS

D2PAK−5

DP SUFFIX

CASE 936AC−01

ISSUE O

For D2PAK Outline and

Dimensions − Contact Factory

PACKAGE THERMAL DATA

Parameter TO−220−5 D2PAK−5 Unit

RqJC Typical 1.4 1.4 °C/W

RqJA Typical 50 10−50* °C/W

*Depending on thermal properties of substrate. RqJA = RqJC + RqCA.

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operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights

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